1. Left-Handed
Metamaterials for
Microwave Engineering
Applications
Department of Electrical Engineering
UCLA

2. Outline
• Left-Handed Metamaterial Introduction
Resonant approach
Transmission line approach
• Composite Right/Left-Handed Metamaterial
• Metamaterial-Based Microwave Devices
Dominant leaky-wave antenna
Small, resonant backward wave antennas
Dual-band hybrid coupler
Negative refractive index flat lens
• Future Trends
• Summary

3. What is a Left-Handed Metamaterial?
μ (Permeability)
re
conventional
fle
plasma d
ct e
cte (RH)
fra
d
wire structure
air air re
nt
ε < 0, μ > 0 ε > 0, μ > 0
ide
n = + εμ
inc
No transmission
ε
(Permittivity)
LHMs
ferrites
ε < 0, μ < 0 split rings structure
air air
ε > 0, μ < 0
n = − εμ No transmission
1967: Veselago speculates about the possibility of LHMs and discusses their properties.

4. What is a Left-Handed Metamaterial?
Veselago’s Conclusions
• Simultaneous negative permittivity (-ε) and permeability (-μ).
• Reversal of Snell’s Law (negative index of refraction), Doppler
Effect, and Cerenkov Effect.
• Electric field, Magnetic field, and Wavevector of electromagnetic
wave in a LHM form a left-handed triad.
• LHMs support backward waves: anti-parallel group and phase
velocity.
• Artificial effectively homogenous structure: metamaterial.

5. Rectangular Waveguide Filled with LHM
→
Pin k backward wave (vp = -vg)
ε>0, μ>0 →
k
→
→ ε<0, μ<0
k
S
LH Triad ε>0, μ>0
→
S
Pout
→
S
HFSS simulation using effective medium [1]
naturally occurring LH material has not yet been discovered

6. LHM – Resonant Approach
• 1967: LHM were first proposed by Russian Physicist Victor Veselago
• 2001: LHM realized based on split ring resonators - Resonant Approach towards LHMs [2].
SRR
metal wire
SRR-based LHM unit-cell
SRR: at resonance provides μ<0
metal wire: provides ε<0
• SRR-based metamaterials only exhibit LH properties at resonance - inherently narrow-band
and lossy.
• SRR-based LHMs are bulky - not practical for microwave engineering applications.

7. LHM – Transmission Line Approach
• Backward wave transmission line can form a non-resonant LHM [3]-[4].
• Transmission Line Approach is based on the dual of a conventional transmission line.
Series capacitance (CL) and shunt
CL CL CL inductance (LL) combination
supports a fundamental backward
wave.
LL LL −1
β=
Perfect LH transmission line ω C L LL
• Perfect LH transmission line not resonant dependent - low-loss and broad-band performance.
• However, perfect LH transmission line is not possible due to unavoidable parasitic right-
handed (RH) effects occurring with physical realization.

8. Transmission Line Approach
PRH TL LR PLH TL CL
... CR ... ... LL . ..
1
β PRH = ω CR LR β PLH = −
ω CL LL
ω ω
−βc +βc −βc +βc
β β

9. Composite Right/Left-Handed Metamaterial
ω = −βc ω ω = + βc 0 0
CL LR
CR LL
CRLH
RH
β = s(ω ) ω 2C R LR +
1 ⎛L C ⎞
− ⎜ R + R ⎟,
ω 2C L LL ⎜ LL C L ⎟
β
⎝ ⎠
• Low frequencies: supports
⎧ − 1 if ω < min(ω se , ω sh ) ⎫ backward wave
s (ω ) = ⎨ ⎬,
⎩ + 1 if ω > max(ω se , ω sh )⎭
• High frequencies: supports forward
where wave
1 1
ωse = and ω sh = • Two cases
C L LR C R LL Unbalanced: ωse≠ ωsh
Balanced: ωse= ωsh0

10. CRLH Metamaterial
1 2 3 N
p
Homogeneity Condition
• Long wavelength regime
CRLH TL
• p < λg/4
0 L = N*p

11. CRLH Metamaterial – Physical Realization
CL LR capacitors
metal pads
(provides RH effects)
CR LL inductor
via to gnd
Composite right/left-handed (CRLH) unit-cell Lumped element implementation
Distributed microstrip implementation Distributed microstrip implementation based
based on interdigital capacitor on Sievenpiper mushroom structure [5]

12. CRLH – Implementation and Analysis
Cascade periodic unit-cell to form one- or two-dimensional CRLH metamaterial TL.
How to Characterize a CRLH Unit-Cell
Propagation Constant – Dispersion Diagram
Impedance – Bloch Diagram

13. Comparison of LHMs to PBGs and Filters
Photonic Bandgap (PBG) Filters
period
Similarities Similarities
• periodic structures • periodic structures
• can be more than one-dimensional • based on low-pass/high-pass structures
Differences Differences
• PBGs have to be periodic; lattice period • Filters generally designed to meet magnitude
determines scattering specifications; LHMs designed to meet both
• PBG operated at frequencies where lattice magnitude and phase.
period is multiple of λg/2; LHMs operated at • Node-to-node phase shifts of 180° required
frequencies where period < λg/4. for filters.
• LHMs can be one-, two-, or three-
dimensional and are used as bulk “mediums.”

14. Dominant-Mode Leaky Wave Antenna

15. Leaky-Wave Antenna Theory
Principle
Conventional RH Leaky-Wave Antenna z ko
(operated at higher-order mode)
kz
θ
β
source x
θ = asin(β (ω ) k0 )
CRLH Leaky-Wave Antenna [6]
(operated at dominant mode) kz2= ko2- β2
ω = − β c0 ω ω = + β c0
Characteristics:
II III
LH RH • Operating in leaky regions
RAD. RAD.
II : BACKWARD ( β < 0 )
CRLH
I IV RH
III : FORWARD ( β > 0 )
LH RH
GUIDANCE GUIDANCE • BROADSIDE radiation ( β = 0 )
ω0
balanced case: vg(β = 0 ) ≠ 0
β • Fundamental mode

16. 1-D Dominant Mode Leaky-Wave Antenna
3-D Far-field Pattern for Several Frequencies
Design Specifications
fo = 2.4 GHz
ZB = 50 Ω
unit-cell
P in
frequency beam scanning
Backfire – to – Endfire

17. Design Flow
Unit-cell parameter – Design Guidelines
Dispersion/Bloch Diagrams – Driven Mode
Optimize unit-cell for specifications
Cascade unit-cells to form CRLH transmission line
Simulate CRLH transmission line
• S-Parameters: matching
• Far-field: fast-wave region for leaky-wave application

18. 1-D CRLH Unit-Cell (Interdigital)
• Distributed unit-cell p
series capacitance provided by
interdigital capacitor
shunt inductance provided
from shorted stub
w
shunt capacitance from top
metal to ground plane
series inductance from current
on interdigital capacitor ls
lc
Variables Initial Design Final Design
unit-cell period p 12.3 mm 11.4 mm
stub length ls 10.0 mm 10.9 mm
stub width ws 1.00 mm 1.00 mm via
interdigital finger length lc 10.5 mm 10.2 mm
interdigital finger width wc 0.30 mm 0.30 mm
spacing between fingers S 0.20 mm 0.20 mm
via radius r 0.12 mm 0.12 mm ws
substrate height h 1.57 mm 1.57 mm
substrate permittivity εr 2.2 2.2

19. 1-D CRLH Unit-Cell Design Guidelines*
For 2-D space scanning, we need to design a balanced (ωse = ωsh) CRLH unit-
cell so that there is a seamless transition from LH to RH operation.
1. Choose center frequency, fo, which 5. Set the number of fingers, N, to 8 or 10.
represents broadside radiation. (fo=2.4 Then determine required wc and S=2wc/3.
GHz) N=10 chosen.
w
2. Calculate width required to obtain Zo, set w wc ≈ ≈ 0.3 mm
to this value. (w~5.0 mm) ⎛ 5N 2 ⎞
⎜ − ⎟
⎝ 3 3⎠
3. Set stub width, ws, to 20% of w. (ws=1.0
mm) S = 0.2 mm
4. Set stub length (lsi=ls- w) to w; the electrical 6. Calculate length of interdigital finger.
length of the stub has to be less than π/2.
λg co
lc ≈ ≈ ≈ 10.5 mm
8 8 fo ε r
* Guidelines have been test on Rogers Duroid 5870 (er=2.33) and 5880 (er=2.2) for various substrate
heights; for high permittivity substrate, the number of fingers should be reduced.

20. Dispersion/Bloch Diagram Extraction
Design Specifications
fo = 2.4 GHz
ZB = 50 Ω
extra section of mircostrip (5 mm each)
Planar EM simulation
⎛ 1 − S11S 22 + S12 S 21 ⎞
βp = cos ⎜
⎜
−1
⎟
⎟
S-Parameter extraction ⎝ 2 S 21 ⎠
2 jZ o S 21 sin( β p )
ZB =
(1 − S11 )(1 − S 22 ) − S 21S12

21. Dispersion Diagram Extraction
Setup dispersion equation; this can be obtained directly from the S-parameters.
⎛ 1 − S11S 22 + S12 S 21 ⎞
βp = cos ⎜
⎜
−1
⎟
⎟
⎝ 2 S 21 ⎠
Go to Results > Create Report
Then click on Output Variables

22. Dispersion Diagram
Final Design Dispersion Diagram in Ansoft Designer
fast-wave region
beta < ko self resonance
of interdigital capacitor
slow-wave region
e
lin
beta > ko
air

23. Bloch Impedance Diagram
Resulting Bloch Impedance Diagram in Ansoft Designer
Re(ZB)
Im(ZB)
impedance (Ohm)
LH RH
fast-wave region fast-wave region

24. 10-Cell CRLH Leaky-Wave Antenna
Port1 Port2
Return/Insertion Loss
Insertion loss
Return loss
LH RH
fast-wave region fast-wave region

25. 10-Cell CRLH Leaky-Wave Antenna
Far-field Pattern for Several Frequencies
Backward: f=1.95 GHz
Broadside: f=2.35 GHz
Forward: f=2.95 GHz

26. Small Metamaterial Antennas

27. Resonant Antenna Theory
Conventional RH Patch Antenna CRLH Patch Antenna
(treat as periodic, consisting of 2 RH “unit-cells”) (2 CRLH unit-cells)
RH p CRLH p
resonance condition
RH p nπ CRLH p
βn =
2p
ω
n = +1, +2, … n=+1 n = 0, ±1, ±2, …
CRLH can have same half-
n=+1 wavelength field distribution, but
n=-1
at much lower frequency
βp
0 π/2 π

28. 1.0 GHz CRLH n=-1 Antenna [7]
for 4 unit-cells
5
Initial dispersion curve
4 Increase LL
Frequency (GHz)
Increase CL
3 Increase CL & LL
2
1
0
0 0.25 0.5 0.75 1
β∗ρ/π n= -1 mode is used
h1 = 3.16 mm
MIM 12.2 mm h2 = 0.254 mm
Capacitance z y
15 mm
x
CPW stub
h2
h1
1/19λ0 x 1/23λ0 x 1/88λ0
ground CWP feed

29. 1.0 GHz CRLH n=-1 Antenna [7]
0
-5
n = -3 top view
Return Loss (dB)
-10 n = -2
-15
-20
n = -1
measurement HFSS
-25
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5
Frequency (GHz)
E-copol (x-z plane) H-copol (y-z plane) back view
E-xpol (x-z plane) H-xpol (y-z plane)
90 90
-5 -5
-10
135 -15
45 135 -10 45
-20 -15
-25 -20
-30 -25
-35
-30
-40
-45 -35
-50 -40 -35 -30 -25 -20 -15 -10 -5
-45 -40-35 -30 -25 -20 -15 -10 -5
180 0 180 0
225 315 225 315
270 270

30. CRLH n=0 Antenna (Monopolar) [8]
Experimental Results
6 4.0
3.8
Frequency (GHz)
Peak Gain (dBi)
4
3.6
3.4
2
ω
3.2
ω = − β c0 ω = + β c0 Exp. Peak Gain
Exp. Resonant Frequency
0 3.0
2 4 6
# of unit-cells (N)
n=0 points
As N increases…
CRLH • Gain increases.
RH
• Resonant frequency does not
β change much.

31. CRLH n=0 Antenna (Monopolar)
z z
0 0
330 30 330 30
0 0
-10 -10
300 60 300 60
-20 -20
-30 -30
z
-40 270 90
x -40 270 90 y
-30 x -30
-20 -20
-10
240 120 y -10
240 120
0 num. 0 num.
210 150 210 150
180 exp. 180 exp.
x Θ, φ
0 0
330 30 330 30
0 0
-10 -10
300 60 300 60
-20 -20
-30 -30
-40 270 90 y -40 270 90
-30 -30
-20 -20
240 120 240 120
-10 -10
0 num. 0 x-z plane
210 150 210 150
180 exp. 180 y-z plane
x-y plane
Cross-Pol

32. Dual-/Multi-Band Metamaterial
Components

33. Dual-Band Hybrid Coupler
CRLH / CRLH hybrid [9]
360
1 CRLH 2 Conventional quadrature:
270 restricted to odd harmonics
because only control on slope
CRLH CRLH
180
4 CRLH 3 DC offset
90
Characteristics: f0 f1 f 2CRLH f 2conv = 3 f1
0 f
• dual-band functionality for an
arbitrary pair of frequencies f1, f2 −90
• principle: transition frequency (fo)
−180
provides DC offset additional degree
of freedom with respect to the
−270 conv. RH
phase slope CRLH
• applications in multi-band systems −360

34. Dual-Band Hybrid Coupler
Branch Line
in Z0 out Experimental Results
0
2
-5
S-parameters (dB)
LH
TLs -10
Z0 Z0
Z0 -15 f2
= 1.89 S11
2 f1 S21
isolated out -20
S31
S41
-25
Band # 1: 0.92 GHz 0.6 0.8 1 1.2 1.4 1.6 1.8 2
frequency (GHz)
Band # 2: 1.74 GHz

35. Negative Refractive Index Lenses

36. Negative Refractive Index Flat Lens [10]
(nLH)sinθLH = (nRH) sinθRH Effective medium HFSS simulation
RHM
source
(15 mm from interface)
LHM
θRH θLH
RH medium LH medium
refractive index nRH > 0 refractive index nLH < 0
Possibility of realizing a flat lens
E-field magnitude
RH medium RH medium 1
LH medium RH medium 2

37. Two-Dimensional CRLH Realization
Based on Sievenpiper High-Impedance Structure
patch
LR C
L
p
p CR LL via
period of unit cell
ground plane
How to obtain dispersion characteristics?
1. Drivenmode Approach – Simple, quick, 1-D dispersion diagram.
2. Eigenmode Approach – Requires more processing time, accounts for
mode coupling, 2-D dispersion diagram.

38. Unit-Cell Setup: Physical Details
metal patch
metal via
radius = 0.12 mm t
mm =4.8
height = 1.27 mm .8 mm
t=4
h=1.27 mm
z
p=
5.0 mm
mm .0
p =5
substrate parameters ground plane x y
εr=10.2, tanδ=0.0023 Np/m
* patch,via, and ground plane are assigned as copper.

39. Design Flow
Unit-Cell Parameters – 1st Order Calculation
Dispersion Characteristics
Design
Driven Mode Approach Verify Eigen Mode Approach
• 1-D dispersion • 2-D dispersion
• No mode coupling • Mode coupling
Flat Lens Realization – Phase Matching
HFSS Simulation Flat Lens
• Symmetry Conditions: Reduce Simulation Time
• Field Plots: Magnitude & Phase

40. Sievenpiper Unit-Cell: 1st Order Calculation
distributed unit-cell equivalent circuit model
fsh = 1/{2πsqrt(CR x LL)}
series capacitance: CR ~ substrate permittivity x (patch area/substrate height)
shunt inductance: LL ~ 0.2 x substrate height x ln[(2 x substrate height/via radis) – 1]
* Left-handed mode will always occur below the shunt resonance (ωsh). Therefore,
design dimensions such that wsh occurs at higher limit of frequency of interest.
fsh ~ 5 GHz for the dimensions shown in previous slide.

41. Sievenpiper Unit-Cell: Driven Mode
gap=0.2 mm • Modify unit-cell so that ports
can be placed on it, while
via keeping dimensions the same.
Unit-cell becomes asymmetrical.
Port 2
Port 1
• Run driven mode solution; set
mesh frequency to ωsh from 1st
order calculation.
p=5.0 mm • Obtain S-parameters, use
following expression to calculate
propagation constant.

42. Sievenpiper Unit-Cell: Driven Mode
1-D dispersion diagram (from Port 1 to Port 2)
e
lin
air right-handed mode
band-gap
left-handed mode

43. Eigenmode Solver: 2-D Dispersion Diagram
z
x y
Γ
Γ to X: px=0°, py=0°→180°
X X to M: px=0°→180°, py=180°
M M to Γ : px, py: 0°→180°
• px: phase offset in x-direction
• py: phase offset in y-direction
Use Linked Boundary Conditions (LBCs) in HFSS to apply required phase shifts.

44. Sievenpiper Unit-Cell Setup
Airbox and PML Setup
1. Create airbox1.
2. Select top face of airbox1 and
assign PML.
3. Create airbox2.
PML hPML=2.50 mm
airbox2
hairbox1=8.00 mm
airbox1
z
physical dimensions
shown in previous slide x y

45. Unit-Cell Setup: Linked Boundaries
XZ - Planes YZ - Planes
mx my
sx z sy
x y
Slave BC: sx Slave BC: sy
• phase delay: px (180 deg) • phase delay: py (0 deg)

46. Eigenmode 2-D Dispersion Diagram
Plotted in Microsoft Excel
5
4
frequency (GHz)
3
2
1
0
Γ X M Γ

47. Dispersion Comparison: 1-D vs 2-D Solve
8
7
Drivenmode
frequency (GHz)
6
Eigenmode (2D)
5
4
3
2
1
0
0 90 180
Beta*p (deg)
Use drivenmode to quickly characterize/design, eigenmode to verify

48. Flat Lens – Physical Realization
Entire circuit on Roger RT 6010 substrate with εr = 10.2 and h = 1.27mm
PPWG
40.0 mm (n = +3.2) voltage source
15 mm refocus should
occur at 3.8 GHz
50.0 mm
LHM based on
21x10
mushroom unit-cells
(n = -3.2 @ 3.8 GHz)
40.0 mm
PPWG
(n = +3.2)
125.0 mm

49. Flat Lens – Phase Matching Condition
5
phase match at 3.8 GHz
frequency (GHz)
4
|βp| = 72 deg, |n|=3.2
3 X
M
2
1
0
Γ0 30 60 90 120 150 180 210 240 270
βp (deg)

50. Flat Lens – Simulation Setup
Entire circuit on Roger RT 62.5 mm
6010 substrate with
130.0 mm
εr = 10.2 and h = 1.27mm voltage source C
D PPWG
(n = +3.2) 18.0 mm
A
B LHM based on
21x10 mushroom unit-cell
(n = -3.2 @ 3.8 GHz)
Boundary Conditions
• Radiation boundary applied on Top and Side A, B, and C of air box.
• Finite conductivity (Copper) applied on bottom of airbox, PPWG trace, and mushroom patches.
• Symmetry boundary (perfect-H) applied to Side D to reduce problem size.

51. Flat Lens – Field Calculator for Phase
To plot the E-field phase, the field calculator has to be used.
• Go to HFSS > Fields > Calculator
• Since the field is quasi-TEM, only the z-component of the E-field is required.
Quantity > E
Scal? > ScalarZ
Vec? > VecZ
Complex > CmplxPhase
Mag
Add, give name PhazeZ

52. Flat Lens – E-Field Plots (Ground Plane)
field on ground plane @ f=3.75 GHz
Magnitude Phase

53. Flat Lens – E-Field Plots (Above Structure)
field on top of structure @ f=3.75 GHz
(3.5 mm above top metal)
Magnitude Phase

54. Flat Lens – Experimental Results
f0 =3.79 GHz
E-field magnitude
Source Source
E-field phase
E-field measured ~ 3.5 mm above
CRLH region

55. Future Trends

56. Applications & Research
Metamaterial Multiple-Input-Multiple-Output (MIMO)
Arrays for 802.11n Application [11]
Active CRLH Metamaterials
• High-gain leaky-wave antennas (embed amplifiers in unit-cell) [12]
• Distributed amplifiers [13]
Tunable Phase Shifters [14]

57. Implementations
Nano-Metamaterials: optical frequency applications [15]
Evanescent-Mode Metamaterials [16]
1-D LHM: cylindrical DRs in TE mode cutoff
parallel plate waveguide (-ε)
H-field Profile (TE01δ mode, -μ)
Three-Dimensional Metamaterials [17]

58. Summary
• Left-Handed Metamaterial Introduction
Resonant approach
Transmission line approach
• Composite Right/Left-Handed Metamaterial
• Metamaterial-Based Microwave Devices
Dominant leaky-wave antenna
Small, resonant backward wave antennas
Dual-band hybrid coupler
Negative refractive index flat lens
• Future Trends

59. 1)
References
C. Caloz, C.C. Chang, and T. Itoh, “’Full-wave verification of the fundamental properties of left-handed materials (LHMs) in
waveguide configurations,” J. App. Phys., vol. 90, no. 11, pp. 5483-5486, Dec. 2001.
2) R.A. Shelby, D.R. Smith, and S. Schultz, “Experimental verification of a negative index of refraction,” Science, vol. 292, pp. 77-79,
Apr. 2001.
3) A. Lai, C. Caloz, and T. Itoh, “Composite right/left-handed transmission line metamaterials,” IEEE Microwave Magazine, Vol. 5, no.
3, pp. 34-50, Sep. 2004.
4) C. Caloz and T. Itoh, Electromagnetic Metamaterials: Transmission Line Theory and Microwave Applications, Wiley and IEEE
Press, Hoboken, NJ, 2005.
5) D. Sievenpiper, L. Zhang, R.F.J. Broas, N.G. Alexopolous, and E. Yablonovitch, “High-impedance surface electromagnetic surfaces
with a forbidden frequency band,” IEEE Trans. Microwave Theory Tech., vol. 47, no. 11, pp. 2059-2074, Nov. 1999.
6) L. Liu, C. Caloz, and T. Itoh, “Dominant mode (DM) leaky-wave antenna with backfire-to-endfire scanning capability,” Electron. Lett.,
vol. 38, no. 23. pp. 1414-1416, Nov. 2002.
7) C.J. Lee, K.M.K.H. Leong, and T. Itoh, “Design of resonant small antenna using composite right/left-handed transmission line,” Proc.
IEEE Antennas and Propagation Society Int. Symp., Washington D.C., Jun. 2005.
8) A. Lai, K.M.K.H. Leong, and T. Itoh, “Infinite wavelength resonant antennas with monopolar radiation patterns based on periodic
structures,” IEEE Trans. Antennas Propag., vol. 55, no. 3, pp. 868-876, Mar. 2007.
9) I. Lin, C. Caloz, and T. Itoh, “A branch-line coupler with two arbitrary operating frequencies using left-handed transmission lines,”
IEEE-MTT Int. Symp. Dig., Philadelphia, PA, Jun. 2003, vol. 1, pp. 325–327.
10) A. Lai, “Theory and design of composite right/left-handed metamaterial-based microwave lenses," Master Thesis, Dept. E. E.,
UCLA, Los Angeles, CA, 2005.
11) Rayspan Corporation, http://www.rayspan.com
12) F. P. Casares-Miranda, C. Camacho Peñalosa, and C. Caloz, “High-gain active composite right/left-handed leaky-wave antenna,”
IEEE Trans. Antennas Propag., vol. 54, no. 8, pp. 2292-2300, Aug. 2006.
13) J. Mata-Conteras, T. M. Martìn-Guerrero, and C. Camacho-Peñalosa, “Distributed amplifiers with composite right/left-handed
transmission lines,” Microwave Opt. Technol. Lett., vol. 48, no. 3, pp. 609-613, March 2006.
14) E.S. Ash, “Continuous phase shifter using ferroelectric varactors and composite right-left handed transmission lines,” Master Thesis,
Dept. E.E., UCLA, Los Angeles, CA 2006.
15) V.A. Podolskiy, A.K. Sarychev, and V.M. Shalaev, “Plasmon modes in metal nanowires and left-handed materials,” J. Nonlin. Opt.
Phys. Mat., vol. 11, no. 1, pp. 65-74, 2002.
16) T. Ueda, A. Lai, and T. Itoh, “Demonstration of negative refraction in a cutoff parallel-plate waveguide loaded with 2-D square lattice
of dielectric resonators,” IEEE Trans. Microwave Theory Tech., vol. 55, no. 6, pp. 1280-1287, Jun. 2007.
17) M. Zedler, P. Russer, and C. Caloz, “Circuital and experimental demonstration of a 3D isotropic LH metamaterial based on the
rotated TLM scheme,” IEEE-MTT Int'l Symp., Honolulu, HI, Jun. 2007.

60. Design Guide
• Ansoft Designer: 1-D Leaky-Wave Antenna
• Ansoft HFSS: Negative Refractive Index Flat Lens